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smps led lighting IRS2982SPBF 1 2016 -1 - 18 led /smps flyback control ic features ? high voltage fast startup ? voltage mode control ? critical - conduction / t ransition mode operation ? constant voltage / current regulation ? minimum off time (dcm at light load) ? burst mode operation at very light load ? cycle cy cycle o ver - current protection ? open load over voltage protection ? micro - power startup ( 50 a) ? low quiescent current ? latch immunity and esd protection ? noise immunity typical applications ? led drivers ? power supplies product summary topology flyback i o+ & i o - (typical) 200 ma / 4 00 ma t r & t f (typical) 60 ns / 30 ns package 8 - lead soic irs2982 spbf ordering information base part number package type standard pack complete part number form quantity IRS2982SPBF so8n tape and reel 2500 irs2982strpbf
IRS2982SPBF 2 2016-1 - 18 table of contents page description 3 qualification information 5 absolute maximum ratings 6 recommended operating conditions 6 electrical characteristics 7 functional block diagram 9 state diagram 10 input / output pin equivalent circuit diagram 1 1 lead definitions 1 2 lead assignments 1 2 application information and additional details 1 3 performance graphs 17 package details 21 tape and reel details 22 part marking information 23
IRS2982SPBF 3 2016-1 - 18 description the irs2982 is a versatile smps cont rol ic designed to drive switching converter s for led drivers and power supplies . f eatures include ; integrated high voltage start up, accurate temperature compensated internal reference, transconductance type error amplifier , primary sensed open circuit protection and cycle by cycle primary current limiting. the irs2982 is compatible with buck, boost, flyback and other smps circuit topologies and is able to regulate voltage or current directly or by secondary feedback through an opto - isolator. the h igh voltage startup cell enables the vcc supply to be derived initially from the dc bus until an auxiliary inductor winding or other supply source is able to take over enabling rapid start up under all line input voltage conditions . the irs2982 uses voltage mode control operat ing in critical conduction (crcm) with a minimum off time limit so that it enters discontinuous (dcm) mode at light loads. burst mode operation is also available at very light loads. the irs2982 is ideal for single stage converters with an unsmoothed dc bus to obtain high power factor and low line current thd . typical connection diagram s 1. non - isolated flyback led driver ? current regulated dfb t 1 br 1 cin m 1 rg cvout rcs cf rf dvcc ic 1 rled rzx 1 ac line input cco mp rzx 2 cvcc rout radj dsn rsn csn dz rz qvcc cs cs com out vcc comp fb hv zx irs 2982 7 6 5 1 2 3 4 8
IRS2982SPBF 4 2016 -1 - 18 2. isolated flyback smps ? voltage regulated dfb t 1 br 1 cin m 1 rg cvout rcs cf rf dvcc ic 1 rzx 1 ac line input cco mp rzx 2 cvcc rout dsn rsn csn dz rvcc cs + vout - vout rfb 1 rfb 2 ci cs com out vcc comp fb hv zx irs 2982 7 6 5 1 2 3 4 8 3. non - isolated flyback smps ? voltage regulated dfb t 1 br 1 cin m 1 rg cvout rcs cf rf dvcc ic 1 rzx 1 ac line input cco mp rzx 2 cvcc rout dsn rsn csn dz rvcc cs + vout - vout rfb 1 rfb 2 cs com out vcc comp fb hv zx irs 2982 7 6 5 1 2 3 4 8
IRS2982SPBF 5 2016-1 - 18 qualification information ? qualification level industrial ?? comments: this family of ics has passed jedec?s industrial qualification. ir?s consumer qualification level is granted by extension of the higher industrial level. moisture sensitivity level soic8 msl2 ??? 260c (per ipc/jedec j - std - 020) esd machine model class b (per jedec standard jesd22 - a115) human body model class 1c (per eia/jedec standard eia/jesd22 - a114) ic latch - up test class i , level a (per jesd78) rohs compliant yes ? qualification standards can be found at international rectifier?s web site : http://www.irf.com/ product - info/reliability/ ?? higher qualification ratings may be available should the user have such requirements. please contact your int ernational rectifier sales representative for further information. ??? higher msl ratings may be available for the specific package types listed here. please contact your international rectifier sales representative for further information.
IRS2982SPBF 6 2016-1 - 18 absolute maximum ratings absolute maximum ratings indicate sustained limits beyond which damage to the device may occur. all voltage parameters are absolute voltages referenced to com, all currents are defined positive into any lead. the thermal resistance and power dissipation ratings are measured under board mounted and still air conditions. symbol definition min. max. units v cc ic low voltage supply ? --- 20.8 v v out gate driver output voltage - 0.3 v cc + 0.3 io max maxim um allowable output current (out ) due to external power transistor m iller effect - 800 600 ma i cc v cc current 0 25 ma v hv hv pin voltage - 0.3 600 v v comp comp pin voltage - 0.3 v cc + 0.3 v fb fb pin voltage v zx zx pin voltage i comp comp pin current - 5 5 ma i zx zx pin current i cs cs pin current p d package power dissipation @ t a +25oc p d = (t jmax - t a )/r ja (8 - pin soic) --- 0.625 w r ja thermal resistance, ju nction to ambient (8 - pin soic) --- 200 oc/w t j junction temperature - 55 150 oc t s storage temperature - 55 150 t l lead temperature (soldering, 10 seconds) --- 300 ? this ic contains a zener clamp structure between the chip v cc and com which has a nominal breakdown voltage of 20v. this supply pin should not be driven by a dc, low impedance power source greater than the v clamp specified in the electrical characteristics section. recommended operating conditions for proper operation the device should be used within recommended conditions. symbol definition min. max. units v cc supply voltage v ccuv+ 18 v i cc v cc supply current 0 10 ma i cs cs pin current - 1 1 i zx zx pin current v fb fb pin voltage 0 6 .0 v v cs cs pin voltage 0.1 1.3 t j junction temperature - 25 125 oc
IRS2982SPBF 7 2016-1 - 18 electrical characteristics v cc =14v +/ - 0.25v, c out = 1000pf, v comp = v oc = v fb = v zx = 0v, t a =25 ? c unless otherwise specified symbol definition min typ max units test conditions supply characteristics v ccuv + v cc supply under - voltage positive going threshold 11.5 12.5 13.5 v v ccuv - v cc supply under - voltage negative going threshold 9.5 10.5 11.5 v uvhys v cc supply under - voltage lockout hysteresis 1.5 2.0 3.0 i qccuv uvlo mode v cc quiescent current --- 50 200 p a v cc =6v i qc c v cc supply quiescent current 1. 0 0 1. 4 5 2.30 ma v clamp v cc zener clamp voltage 19.8 20.8 21.8 v i cc =10ma high voltage startup characteristics v hvsmin minimum s tartup v oltage 3 0.0 --- --- i hv_charge v cc c harge c urrent 3.2 0 3. 77 4. 3 0 ma v cc =0v v hv s = 50v v hvs_off 1 cut off level in startup mode 17.4 18 18.6 v i hv =100 a gbd v hvs_off 2 cut off level in support mode 12.5 13 13.5 i hvs_off high voltage start - up circuit off state leakage c urrent --- --- 50 p a hv=400v v cc >v hvsoff(max) error amplifier characteristics i vfb input b ias c urrent --- - 1 --- p a v fb =0 to 3v i comp_ source comp pin error amplifier output current sourcing 20 3 3 60 i comp_ sink comp pin error amplifier output current sinking - 60 - 3 3 - 20 v compoh error amplifier output voltage swing (high state) --- 13.5 --- v v compoff cut off voltage below which gate drive output is disabled 1.12 1.40 1.68 v fb = 1.0v v compoff_hys cut off voltage hysteresis --- 40 --- g m trans - conductance --- 100 --- a/v control characteristics v zx+ zx pin threshold voltage (arm) 1.40 1.54 1.68 v v zx - zx pin threshold voltage (trigger) 0.48 0.58 0.66 v ref regulation reference 0.392 0.400 0.408 t blank oc pin current - sensing blank time 160 200 264 ns v fb =1.0v v comp =4.0v v cs =1.5v
IRS2982SPBF 8 2016-1 - 18 electrical characteristics (cont?d) v cc =14v +/ - 0.25v, c out = 1000pf, v comp = v oc = v fb = v zx = 0v, t a =25 ? c unless otherwise specified. symbol definition min typ max units test conditions t wd gate drive restart pulse interval 60 100 130 p s v zx =0 v comp =4.0v t onmin pwm minimum on time 143 168 194 ns t onmax pwm maximum on time 18 30 45 p s v zx =0 v comp =13v t offmin pwm minimum off time 2. 6 0 3. 12 3. 6 0 p s f max maximum switching frequency --- 320 --- khz t onmin and t offmin protection circuitry characteristics v csth cs pin over - current sense threshold 1.14 1.20 1.26 v v ovth zx pin over - voltage comparator threshold 4.85 5.10 5.35 t ovth zx pin over - voltage comparator blanking time --- 100 --- ns gbd gate driver output characteristics (out pin) v ol low - level output voltage --- 0 100 mv i o =0 v oh high - level output voltage --- 0 100 v cc ? v o , i o =0 t r turn - on rise time --- 60 110 ns t f turn - off fall time --- 30 70 i0+ source current --- 200 --- ma i0 - sink current --- 400 --- gbd guaranteed by design
IRS2982SPBF 9 2016-1 - 18 functional block diagram out comp zx vzx + / vzx - vcc cs 5 7 3 4 vov th vcl amp fb 2 hv startup hv 1 vre f vcc 8 com 6 uvlo q s r q restart timer vcs th q s r q se t dominant leading edge blanking minimum off time vcom poff
IRS2982SPBF 10 2016-1 - 18 state diagram uvlo mode icc = iqccuv hvreg = start mode out = low comp = held low power on start mode vcomp rising out = sw itc hin g vcc > vccuv + fault mode out = low comp = vcompoff vzx > vov th current limit out = low vcs > vcsth regulation mode vcomp = steady state out = sw itc hin g hvreg = support m ode vfb > vth vcs < vcsth vcs > vcsth vcs < vcsth vzx > vov th vhv > vhvmin startu p mo de vcomp rising vcomp > vcompoff + vcompoffhys vzx < vov th delay vcc < vccuv - ... from any point t del ay > t wd
IRS2982SPBF 11 2016-1 - 18 input / output pin equivalent circuit diagrams vcc com comp , fb , cs , zx , out esd diode esd diode vclamp
IRS2982SPBF 12 2016-1 - 18 lead definitions symbol description hv high voltage startup input fb feedback input comp compensation and averaging capacitor input zx zero - crossing & over - voltage detection input cs current sensing input com ic power & signal ground out gate driver output vcc logic & low - side gate driver supply lead assignments cs com out vcc comp fb hv zx irs 2982 7 6 5 1 2 3 4 8
IRS2982SPBF 13 2016-1 - 18 application information and additional details the irs2982 is a switched mode controller ic designed primarily for use in buck, boost and flyback led driver s and power supplies . internal high voltage regulator the internal high voltage regulator suppl ies the ic low voltage bias supply vcc during startup , allowing operation directly from a dc input voltage up to 600v. t o begin operating the irs2982 requires vcc to be raised above the under voltage lockout positive threshold (v ccuv+ ) and to continue ope r ating vcc must be maintained above the under voltage lockout negative threshold (v ccuv - ) . the hv regulator enabl es an irs2982 based led driver to start up very rapidly and deliver light within 0.5s of switch on at any line input voltage . when th e switching converter is operating vcc is normally supplied through an auxiliary transformer winding . t he hv regulator switches over to support mode when steady state operation is reached in which vcc is held above v ccuv+ to maintain operation under light load or fault conditions. as well as supplying vcc t he flyback inductor /transformer auxiliary winding provides output voltage and zero - crossing (zx) i nformation for critical conduction mode (crcm) operation . in the event of a short circuit at the output , the vcc supply derived from the auxiliary winding normally collapses below v ccuv- causing the irs2982 to shut off. t he startup sequence then begins again in a continuous ? hiccup ? mode until the short circuit is removed thereby preventing damage to the circuit. figure 1: hv regulator characteristics figure 1 illustrates the characteristics of the high voltage regulat or. at switch on it operates in startup mode in which current is supplied to vcc from the hv input connected to the rectified high voltage bus. the current supplied depends o n the voltage at vcc and gradually fall s as vcc rises until it cuts off completely at v hvs_off1 . during normal ope ration when the voltage at the fb input exceeds vref for the first time the hv regulator switches over to support mode , where current is suppled to vcc only when the voltage drops be low v hvs_off2 , which is close to v ccuv+ . this helps to sustain the vcc supply at light loads such as during dimming. however care should be taken to avoid sustained operation where the hv regulator supplies current to vcc since this will cause the ic case temperature to rise. more information is given in the performance graphs section. voltage/current r egulation the irs2982 may be operated using either a voltage or current feedback loop. examples of each are shown above in the typical application diagrams. the feedback voltage is fed to the fb input of the ic, which is connected to the internal transconductance error amplifier inverting input. the non - inverting i nput is connected to an internal temperature compensated band- gap voltage reference (v ref ) and the output is connected to the compensation (comp) output. the fb input can be derived from a shunt resistor returning led load current to the 0v return in a non- isolated flyback led driver to regulate output current. alternatively it can be fed b y a divider from the transformer auxiliary winding to provide voltage regulation in an isolated power supply or a divider directly from the output in a non - isolated power supply. sensing from the auxiliary winding may require some additional filtering comp onents and does not provide highly accurate regulation of the output voltage. the compensation (comp) voltage determine s the switching cycle on time for voltage mode control. loop compensation is performed by means of the transconductance error amplifier u s ing an external capacitor (ccomp) connected to 0v to realize an integrator to provide a stable error voltage used to control the converter on time. ccomp is typically 1f in high power factor single stage converters . at light loads if v comp drops below v compo ff the irs2982 operates in burst . 0 1 2 3 4 0 2 4 6 8 10 12 14 16 18 20 hv startup current (ma) vcc (v) startup mode support mode
IRS2982SPBF 14 2016-1 - 18 burst mode operation under light load conditions the comp capacitor is discharged by the error amplifier reducing v comp . minimum on time is reached just before v comp falls below v compoff . if the output needs to be reduced further then v comp is driven below v compoff and the gate drive is disabled . gate drive does not start up again until v comp has risen above this value by v compoff_hys at which time it will start to switch at minimum on tim e. during burst mode operation the on time typically remain s at minimum t onmin and the off time is limited to the minimum off time t offmin . switching frequency under these conditions is around 3 2 0khz , which is the maximum possible for the irs2982. the length of each burst and the period between bursts are determined by the value of ccomp in conjunction with the converter output capacitor value. the vcc supply is normally maintained through the auxiliary winding, however if necessary the high voltage reg ulator will supply current to vcc to keep it just above v ccuv - . t tburst v ( t ) vout ( t ) vcomp ( t ) figure 2 : burst mode waveforms primary current limiting primary mosfet current is sensed through a shunt resistor (rcs) connected from the source of the flyback mosfet switch to the dc b us return . this current waveform i s a high frequency ramp rising from zero at the beginning of each switching cycle to reach a peak level at the point the mosfet is switched off and remaining at zero during the off time. at very low input voltages the voltage or current regulation loop would demand a very high peak current, which may exceed t he maximum rating of the transformer . t o prevent saturation from occurring , the irs2982 provides cycle by cycle prima ry current limiting with a threshold v csth at the cs pin input. under low line or fault conditions where the mosfet current is abnormally high the gate drive is switched off after the blan king time t blank . leading edge blanking is n ecessary to avoid false triggering due to the fast high current switch on transient that occurs at switch on of the mosfet resulting from discharge of parasitic capacitances . t ts v(t) vout(t) vcs(t) vcsth figure 3 : cycle by cycle current limiting the irs2982 normally operates in critical conduction mode (crcm), also known as transition or boundary mode. the transformer auxiliary winding provide s a signal to the irs2982 zx input that indicates when all of the energy stored in the inductor has been transferred to the output. this triggers the start of the next switching cycle. the auxiliary winding voltage is divided through rzx1 and rzx2 to provide the zx pin input signal . the pulse amplitude zx i s approxim ately proportional to the secondary output voltage and therefore the dc output voltage: ) 2 1 ( 2 rzx rzx n vout rzx n vzx s a + ? ? ? [1] w here, n a = number of turns on the auxiliary winding n s = number of turns on the secondary winding vout = dc output voltage or led voltage in reality v zx contains high frequency ringing resulting from leakage inductance and circuit
IRS2982SPBF 15 2016-1 - 18 parasitics. this ringing may need to be filtered to provide acceptable output voltage tracking. when the converter mosfet switches off , v zx transitions positively . the values of rzx1 and rzx2 must be selected so that this voltage always exceeds the v zx+ threshold to ensure crcm operation . i f the irs2982 is used in a converter that is required to drive loads over a range of vo ltage such as a constant current regulated led driver, the v zx voltage needs to exceed v zx+ at the minimum load voltage. if v zx does not exceed v zx+ the irs2982 cannot operate in crcm and remains pulsing with the t wd timeout periodically trigger ing the next cycle. in normal crcm w hen v zx exceeds v zx+ the irs2982 waits until the v zx then drops below v zx - again to initiate the next switching cycle . a capacitor may be added in parallel with rzx2 to add a small delay . this may be needed to minimize swit ching loss by enabling switch on to occur at the minimum point or ?valley? of the drain voltage. the irs2982 includes a minimum off time function so that if the zx pin input transitions high and low in less than t offmin , the gate drive output will not transition high again until the end of this period. this prevents false tripping by ringing at the zx input and also limits the converter ma ximum switching frequency by entering dcm under conditions where the off tim e would otherwise be unacceptably short. the minimum off time extends the operating range of the converter allowing operation down to very low duty cycles. this enables dimming designs to be implemented as well as limiting operating frequency to limit switching losses and prevent overheating of the circuit magnetics , the mosfet and snubber components. t ts v ( t ) vout ( t ) vzx ( t ) figure 4 : zero crossing detection the irs2982 may also be used in dcm by driving the zx input from a delay circuit triggered by the falling edge of the gate drive output. a simple circuit is added as shown in figure 5 . as the gate drive goes low a pulse of determined length can be generated to drive zx forcing the system to operate with a fixed off time greater than the preset minimum off time . cin mpfc rpfc rcs cf rf ic 1 cvcc rzx rc rb qzx cc dzx cco mp cs com out vcc comp fb hv zx irs 2982 7 6 5 1 2 3 4 8 figure 5 : dcm operation over voltage protection the zx input is a multi - function input also used for outpu t over voltage limiting. in a flyback converter if the load becomes disconn e cted the output voltage can become very high causing rapid damage to components as well as present ing a possible electrical hazard. in order to protect against this the irs2982 senses the output voltage indirectly through the zx input , since its peak voltage tracks the output voltage. if the zx input voltage exceeds v ovth the gate drive switches off for a t wd period before starting the next cycle . at the same time the comp capaci tor is discharged below v compoff so after a delay the next cycle will begin at minimum duty cycle and ramp up slowly . this protection scheme allows the load to be ? hot ? connected and disconnected from the converter output without ri sk of damaging the circuit by high voltages appearing at the output. care should be taken however to avoid damage to led loads due to output capacitor discharge. an ntc thermistor at the output may be needed to limit the current surge. the overvoltage threshold is set by cho osing the values of rzx1 and r zx2 appropriately, according to the formula:
IRS2982SPBF 16 2016-1 - 18 2 ) 2 1 ( rzx n rzx rzx n vovth vout a s ov ? + ? ? [2] the recommended over voltage threshold is 25% above the normal operating voltage for led load s . t twd v(t) vout(t) vzx(t) vcomp(t) figure 6 : overvoltage protection operating with a secondary feedback circuit in applications where galvanic isolation and accurate voltage and/or current regulation are required, the irs2982 should be used in conjunction with a secondary sensing and feedback circ uit. the feedback circuit is fed throu gh an opto - isolator connected to the irs2982 as follows : a sim ple feed back scheme is shown in figure 7 to illustrate how an opto - isolator may be connected to the irs2982 to create a feedback circuit. the fb input is tied to com leaving the error amplifier inverting input at zero volts so that the comp output provides pull up . the opto - isolator feedback pulls down on the comp voltage to reduce the on time as the opto - diode current is increased driven by a sec ondary error amplifier circuit typically based around the tl431 ic . a pull - up resistor from comp to vcc and a capacitor from comp to 0v are recommended for optimum stability. the irs2982 remains in start mode since the fb input is connected to 0v and can t herefore never rise above the v reg threshold to enter regulation mode. operation in start mode is possible, however vcc should be set to 17v or higher to ensure that only micro current is drawn from the high voltage regulator during steady state operation. this is easily done by using a series pass transistor (qvcc) with the base biased with an 18v zener diode (dzx) to supply vcc. care should be taken to avoid auxiliary winding voltages above 25v to prevent overheating of qvcc. t 1 cin mpfc rpfc rcs cf 2 rf dvcc ic 1 rzx 1 rzx 2 cvcc 2 secondary error feedback dzx qvcc rvcc 2 rvcc 1 cvcc 1 rpu cs com out vcc comp fb hv zx irs 2982 7 6 5 1 2 3 4 8 figure 7 : secondary feedback circuit opto - isolator connection
IRS2982SPBF 17 2016-1 - 18 performance graphs figure 7 : high voltage start up characteristics , ihv vs vcc figure 8 : high voltage start up characteristics, ihv vs vhv 0 0.5 1 1.5 2 2.5 3 3.5 4 4.5 0 1 2 3 4 5 6 7 8 9 10 11 12 13 14 15 16 17 18 19 20 ihv (ma) vcc (v) ihv vs vcc over temperature startup mode 25c support mode 25c startup mode -25c support mode -25c startup mode 125c support mode 125c 0 0.5 1 1.5 2 2.5 3 3.5 4 4.5 5 0 5 10 15 20 25 30 35 40 45 50 55 60 ihv (ma) vhv (v) ihv vs vhv over temperature ihv at 25c ihv at -25c ihv at 125c
IRS2982SPBF 18 2016-1 - 18 figure 9 : high voltage start up characteristics , ihv over t emperature in normal mode figure 10 : high voltage start up characteristics , ihv over t emperature in support mode 0 0.5 1 1.5 2 2.5 3 3.5 4 4.5 5 -40 -20 0 20 40 60 80 100 120 ihv (ma) temperature c ihv vs temperature (normal mode) vcc=0 vcc=2 vcc=4 vcc=6 vcc=8 vcc=10 vcc=12 vcc=14 vcc=16 vcc=18 0 0.5 1 1.5 2 2.5 3 3.5 4 4.5 5 -40 -20 0 20 40 60 80 100 120 ihv (ma) temperature c ihv vs temperature (support mode) vcc=0 vcc=2 vcc=4 vcc=6 vcc=8 vcc=10 vcc=12 vcc=14
IRS2982SPBF 19 2016-1 - 18 figure 11 : under voltage lockout thresholds (vccuv+ and vccuv - ) over temperature figure 12 : over voltage threshold (vov th ) over temperature 9.5 10 10.5 11 11.5 12 12.5 13 13.5 -40 -20 0 20 40 60 80 100 120 voltage temperature c uvlo vs temperature uv+ uv- 4.5 4.6 4.7 4.8 4.9 5 5.1 5.2 5.3 5.4 5.5 -40 -20 0 20 40 60 80 100 120 voltage temperature c vovth vs temperature vov
IRS2982SPBF 20 2016-1 - 18 figure 13 : over current threshold (vcsth) over temperature figure 14 : feedback voltage reference (vfb) over temperature note this measurement is performed by connecting fb and comp together and measuring the voltage at this point, which is not a direct measurement of the reference voltage. 0 0.2 0.4 0.6 0.8 1 1.2 1.4 -40 -20 0 20 40 60 80 100 120 voltage temperature c vcsth vs temperature vcs 0 0.1 0.2 0.3 0.4 0.5 0.6 -40 -20 0 20 40 60 80 100 120 vref temperature c vref vs temperature vref
IRS2982SPBF 21 2016-1 - 18 package details
IRS2982SPBF 22 2016-1 - 18 tape and reel details e f a c d g a b h note : controlling dimension in mm loaded tape feed direction a h f e g d b c carrier tape dimension for 8soicn code min max min max a 7.90 8.10 0.311 0.318 b 3.90 4.10 0.153 0.161 c 11.70 12.30 0.46 0.484 d 5.45 5.55 0.214 0.218 e 6.30 6.50 0.248 0.255 f 5.10 5.30 0.200 0.208 g 1.50 n/a 0.059 n/a h 1.50 1.60 0.059 0.062 metric imperial reel dimensions for 8soicn code min max min max a 329.60 330.25 12.976 13.001 b 20.95 21.45 0.824 0.844 c 12.80 13.20 0.503 0.519 d 1.95 2.45 0.767 0.096 e 98.00 102.00 3.858 4.015 f n/a 18.40 n/a 0.724 g 14.50 17.10 0.570 0.673 h 12.40 14.40 0.488 0.566 metric imperial
IRS2982SPBF 23 2016-1 - 18 part marking information s2982 ir logo yww ? part number date code pin 1 identifier lot code (prod mode ? 4 digit spn code) assembly site code per scop 200-002 ? xxxx marking code lead free released non-lead free released ? p
IRS2982SPBF 24 2016-1 - 18 published by infineon technologies ag 81726 mnchen, germany ? infineon technologies ag 2015 all rights reserved. important notice the information given in this document shall in no event be regarded as a guarantee of conditions or characteristics (?beschaffenheitsgarantie?). with respect to any examples, hints or any typical values stated herein and/or any information regardi ng the application of the product , infineon technologies hereby disclaims any and all warranties and liabilities of any kind, including without limitation warranties of non - infringement of intellectual property rights of any third party. in addition , any information given in this document is subject to customer ?s compliance with its obligations stated in this document and any applicable legal requirements, norms and standards concerning customer?s products and any use of the product of infineon technologi es in customer?s applications. the data contained in this document is exclusively intended for technically trained staff. it is the responsibility of customer?s technical departments to evaluate the suitability of the product for the intended application and the completeness of the product information given in this document with respect to such application. for further information on the product, technology, delivery terms and conditions and prices please contact your nearest infineon technologies o ffice ( www.infineon.com ). warnings due to technical requirements products may contain dangerous substances. for information on the types in question please contact your nearest infineon technologies o ffice. except as otherwise explicitly approved by infineon technologies in a written document signed by authorized representatives of infineon technologies, infineon technologies? products may not be used in any applications where a failure of the product or any conseq uences of the use thereof can reasonably be expected to result in personal injury.

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